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ADA4666-2 Datasheet(PDF) 25 Page - Analog Devices

Part # ADA4666-2
Description  18 V, 725 A, 4 MHz CMOS RRIO Operational Amplifier
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Manufacturer  AD [Analog Devices]
Direct Link  http://www.analog.com
Logo AD - Analog Devices

ADA4666-2 Datasheet(HTML) 25 Page - Analog Devices

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Data Sheet
ADA4666-2
Rev. 0 | Page 25 of 32
EMI REJECTION RATIO
Circuit performance is often adversely affected by high frequency
electromagnetic interference (EMI). When the signal strength is
low and transmission lines are long, an op amp must accurately
amplify the input signals. However, all op amp pins—the
noninverting input, inverting input, positive supply, negative
supply, and output pins—are susceptible to EMI signals. These
high frequency signals are coupled into an op amp by various
means, such as conduction, near field radiation, or far field
radiation. For instance, wires and PCB traces can act as antennas
and pick up high frequency EMI signals.
Amplifiers do not amplify EMI or RF signals due to their
relatively low bandwidth. However, due to the nonlinearities of
the input devices, op amps can rectify these out-of-band signals.
When these high frequency signals are rectified, they appear as
a dc offset at the output.
To describe the ability of the ADA4666-2 to perform as
intended in the presence of electromagnetic energy, the
electromagnetic interference rejection ratio (EMIRR) of the
noninverting pin is specified in Table 2, Table 3, and Table 4 of
the Specifications section. A mathematical method of
measuring EMIRR is defined as follows:
EMIRR = 20 log (VIN_PEAK/ΔVOS)
Figure 78. EMIRR vs. Frequency
CURRENT SHUNT MONITOR
Many applications require the sensing of signals near the
positive or negative rail. Current shunt monitors are one such
application and are mostly used for feedback control systems.
They are also used in a variety of other applications, including
power metering, battery fuel gauging, and feedback controls in
electrical power steering. In such applications, it is desirable to
use a shunt with very low resistance to minimize the series
voltage drop. This not only minimizes wasted power but also
allows the measurement of high currents while saving power.
The low input bias current, low offset voltage, and rail-to-rail
feature of the ADA4666-2 makes the amplifier an excellent
choice for precision current monitoring.
Figure 79 shows a low-side current sensing circuit, and Figure 80
shows a high-side current sensing circuit. Current flowing
through the shunt resistor creates a voltage drop. The ADA4666-2,
configured as a difference amplifier, amplifies the voltage drop
by a factor of R2/R1. Note that for true difference amplification,
matching of the resistor ratio is very important, where R2/R1 =
R4/R3. The rail-to-rail output feature of the ADA4666-2 allows
the output of the op amp to almost reach its positive supply.
This allows the current shunt monitor to sense up to approximately
VSY/(R2/R1 × RS) amperes of current. For example, with VSY =
18 V, R2/R1 = 100, and RS = 100 mΩ, this current is approxi-
mately 1.8 A.
Figure 79. Low-Side Current Sensing Circuit
Figure 80. High-Side Current Sensing Circuit
ACTIVE FILTERS
Active filters are used to separate signals, passing those of
interest and attenuating signals at unwanted frequencies. For
example, low-pass filters are often used as antialiasing filters in
data acquisition systems or as noise filters to limit high
frequency noise.
The high input impedance, high bandwidth, low input bias
current, and dc precision of the ADA4666-2 make it a good fit
for active filters application. Figure 81 shows the ADA4666-2 in
a four-pole Sallen-Key Butterworth low-pass filter configuration.
The four-pole low-pass filter has two complex conjugate pole
pairs and is implemented by cascading two two-pole low-pass
filters. Section A and Section B are configured as two-pole low-
pass filters in unity gain. Table 8 shows the Q requirement and
pole position associated with each stage of the Butterworth
filter. Refer to Chapter 8, “Analog Filters,” in Linear Circuit
Design Handbook, available at www.analog.com/AnalogDialogue,
for pole locations on the S plane and Q requirements for filters
of a different order.
20
40
60
80
100
120
140
10M
100M
1G
10G
FREQUENCY (Hz)
VSY = 3V TO 18V
VIN = 100mV PEAK
VIN = 50mV PEAK
SUPPLY
RL
RS
R1
R2
R4
R3
VSY
I
I
VOUT*
1/2
ADA4666-2
*VOUT = AMPLIFIER GAIN × VOLTAGE ACROSS RS = R2/R1 × RS × I
1/2
ADA4666-2
SUPPLY
RL
RS
R3
R4
R2
R1
VSY
I
I
VOUT*
*VOUT = AMPLIFIER GAIN × VOLTAGE ACROSS RS = R2/R1 × RS × I


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