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ADA4666-2 Datasheet(PDF) 25 Page - Analog Devices |
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ADA4666-2 Datasheet(HTML) 25 Page - Analog Devices |
25 / 32 page Data Sheet ADA4666-2 Rev. 0 | Page 25 of 32 EMI REJECTION RATIO Circuit performance is often adversely affected by high frequency electromagnetic interference (EMI). When the signal strength is low and transmission lines are long, an op amp must accurately amplify the input signals. However, all op amp pins—the noninverting input, inverting input, positive supply, negative supply, and output pins—are susceptible to EMI signals. These high frequency signals are coupled into an op amp by various means, such as conduction, near field radiation, or far field radiation. For instance, wires and PCB traces can act as antennas and pick up high frequency EMI signals. Amplifiers do not amplify EMI or RF signals due to their relatively low bandwidth. However, due to the nonlinearities of the input devices, op amps can rectify these out-of-band signals. When these high frequency signals are rectified, they appear as a dc offset at the output. To describe the ability of the ADA4666-2 to perform as intended in the presence of electromagnetic energy, the electromagnetic interference rejection ratio (EMIRR) of the noninverting pin is specified in Table 2, Table 3, and Table 4 of the Specifications section. A mathematical method of measuring EMIRR is defined as follows: EMIRR = 20 log (VIN_PEAK/ΔVOS) Figure 78. EMIRR vs. Frequency CURRENT SHUNT MONITOR Many applications require the sensing of signals near the positive or negative rail. Current shunt monitors are one such application and are mostly used for feedback control systems. They are also used in a variety of other applications, including power metering, battery fuel gauging, and feedback controls in electrical power steering. In such applications, it is desirable to use a shunt with very low resistance to minimize the series voltage drop. This not only minimizes wasted power but also allows the measurement of high currents while saving power. The low input bias current, low offset voltage, and rail-to-rail feature of the ADA4666-2 makes the amplifier an excellent choice for precision current monitoring. Figure 79 shows a low-side current sensing circuit, and Figure 80 shows a high-side current sensing circuit. Current flowing through the shunt resistor creates a voltage drop. The ADA4666-2, configured as a difference amplifier, amplifies the voltage drop by a factor of R2/R1. Note that for true difference amplification, matching of the resistor ratio is very important, where R2/R1 = R4/R3. The rail-to-rail output feature of the ADA4666-2 allows the output of the op amp to almost reach its positive supply. This allows the current shunt monitor to sense up to approximately VSY/(R2/R1 × RS) amperes of current. For example, with VSY = 18 V, R2/R1 = 100, and RS = 100 mΩ, this current is approxi- mately 1.8 A. Figure 79. Low-Side Current Sensing Circuit Figure 80. High-Side Current Sensing Circuit ACTIVE FILTERS Active filters are used to separate signals, passing those of interest and attenuating signals at unwanted frequencies. For example, low-pass filters are often used as antialiasing filters in data acquisition systems or as noise filters to limit high frequency noise. The high input impedance, high bandwidth, low input bias current, and dc precision of the ADA4666-2 make it a good fit for active filters application. Figure 81 shows the ADA4666-2 in a four-pole Sallen-Key Butterworth low-pass filter configuration. The four-pole low-pass filter has two complex conjugate pole pairs and is implemented by cascading two two-pole low-pass filters. Section A and Section B are configured as two-pole low- pass filters in unity gain. Table 8 shows the Q requirement and pole position associated with each stage of the Butterworth filter. Refer to Chapter 8, “Analog Filters,” in Linear Circuit Design Handbook, available at www.analog.com/AnalogDialogue, for pole locations on the S plane and Q requirements for filters of a different order. 20 40 60 80 100 120 140 10M 100M 1G 10G FREQUENCY (Hz) VSY = 3V TO 18V VIN = 100mV PEAK VIN = 50mV PEAK SUPPLY RL RS R1 R2 R4 R3 VSY I I VOUT* 1/2 ADA4666-2 *VOUT = AMPLIFIER GAIN × VOLTAGE ACROSS RS = R2/R1 × RS × I 1/2 ADA4666-2 SUPPLY RL RS R3 R4 R2 R1 VSY I I VOUT* *VOUT = AMPLIFIER GAIN × VOLTAGE ACROSS RS = R2/R1 × RS × I |
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